Multiple Frequency Cancellation Method for Stealth Design of UWB End-Fire Antenna Array

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College of Electronic and Information Engineering, Nanjing University of Aeronautics and Astronautics, Nanjing 211106, P.R.China

(Received 19 July 2016; revised 17 October 2016; accepted 21 September 2017)

Abstract:A multiple frequency cancellation (MFC) method is proposed for stealth design of ultra-wide band (UWB) end-fire antenna array. The proposed method can produce significant radar cross section (RCS) reduction in the whole operating band. The 1×4 and 4×4 Vivaldi antenna arrays of different kinds of cancellation structures are discussed as examples to validate the effectiveness of the MFC method on both linear and planar arrays. On average, 22.6 dB reduction of monostatic radar cross section (MRCS) is obtained in the whole X-band. MRCS under oblique incident waves is also reduced within ±60°. Basically favorable radiation characteristics are maintained.

Key words:stealth design; antenna array; ultra-wide band (UWB); multiple frequency cancellation (MFC)

0 Introduction

Ultra-wide band (UWB) antenna arrays have been typically applied to fire control system of aircraft and high-data rate wireless communications[1]. However, due to their great contribution to the total radar cross section (RCS), carriers are vulnerable to the enemy in the battlefield. Therefore, it is important to control the strong scattering of UWB antenna arrays in-band. For the out-band, the RCS can be reduced by employing frequency selective surface (FSS) radome[2].

Various stealth design methods have been investigated, most of which focus on the study of antenna element. Structures, such as electromagnetic band-gap (EBG)[3], artificial magnetic conductor (AMC)[4], and phase-switched screen (PSS)[5], are widely applied to the antenna stealth design. These materials usually perform spatial and filtering functions. Recently, structural modification seems to be an effective way to realize low profile characteristics[6-8]. By altering the shapes of UWB antennas, the bionics is integrated in antenna stealth design where a clover-disc monopole antenna[6], an insect tentacle antenna[7], and a plant blades YAGI-UDA antenna[8]are presented with low RCS feature, respectively. On the other hand, Refs.[9-12] attempt to lower the RCS from the perspective of overall antenna array rather than single element. However, all the in-band stealth design methods mentioned above are subject to narrow bandwidth or complexity in antenna designs and manufactures.

To avoid these drawbacks, Chen et al.[13]present a universal method to reduce the RCS of antenna array with the help of cancellation theory. By employing ladder arrangement, they lower the structural mode RCS of antenna array in the whole X-band. Since the “ladder” is designed at only one frequency of 10 GHz, significant RCS reductions are confined to separated narrow bands. Although, the maximum 16.3 dB RCS reduction is achieved on the 3×7 Vivaldi antenna array, the minimum value of RCS reduction is only 1.5 dB[13]. Thus, the stealth performance is unstable when the antenna array is exposed to broadband detecting wave.

In this paper, multiple frequency cancellation (MFC) points are employed to achieve significant RCS reduction over the whole operating band of UWB end-fire antenna array. The proposed MFC method ensures that the antenna array keeps low profile under broadband detecting wave.

1 Stealth Design Method

Fig.1 Schematic of 1×4 antenna array with MFC

The schematic of structure with MFC is shown in Fig.1.didenotes a quarter wavelength of cancellation frequencyfi. Antennas 1 and 2 have a distance ofdiinZ-direction, which forms a cancellation structure at frequencyfi. For an incident plane wave fromZ-direction, the back scattering waves of the two antennas share the same magnitude but have 180° phase difference at frequencyfi, and as a result, cancel each other out[13]. Consequently, the structure mode RCS reduction will be achieved near the cancellation frequency. But the radiation waves of the two antennas also have 90° phase difference. Fortunately, such problem can be eliminated by phase compensation in source. In the same way, Antennas 2, 3 and 4 form another two cancellation structures at frequencyf2andf3. Although each cancellation structure alone operates at separated narrow bands, whenf1,f2, andf3are set close to each other, several narrow bands can be combined together to form a wider one. One step further, in large-scale antenna arrays, such cancellation structure can be employed by all of the adjacent elements. If theZ-coordinate of each element is properly designed, the cancellation frequency points can contribute to significant RCS reduction in the whole operating band of UWB antenna array. Therefore, the end-fire antenna array with MFC can keep in low profile under the whole-band detecting waves.

The cancellations will also exist at frequenciesN×fi(N=3,5,7,…) or between non-adjacent elements, e.g. Antennas 1 and 3. As the corresponding frequencies are usually out of the operating band, such cancellations are not considered in the design.

2 Analysis and Results

The Vivaldi antenna proposed in Ref.[14] is chosen as the element of the following arrays. As shown in Fig.2 witha=20 mm,b=25.2 mm,d=3.8 mm,z1=11.4 mm,z2=2.8 mm,l1=10.05 mm,l2=1.8 mm,l3=1 mm,t1=0.6 mm,t2=0.28 mm,r=2.8 mm, the substrate thickness is 0.635 mm. The substrate thickness is 0.635 mm. The metal patch and the feeding structure are printed on each side of a FR-4 substrate. In the front view, the tapered slot line consists of two parts. The first part is determined by functiony1(z)=0.14e0.27z(0

Fig.2 Geometry of Vivaldi antenna

Fig.3 Return loss for the antenna shown in Fig.2

To understand the effect of MFC method, we consider a 1×4 Vivaldi antenna array as shown in Fig.1. The distance between elements inX-direction is 21 mm which is 0.7 times the wavelength corresponding to 10 GHz. We setd1=9.375 mm,d2=6.25 mm, andd3=18.75 mm, which corresponds to a quarter wavelength atf1=8 GHz,f2=12 GHz, andf3=4 GHz, respectively. The large frequency space can help distinguish each cancellation point from the other. For a co-polarized incident wave in grazing angle, the monostatic radar cross section (MRCS) according to the frequency is shown in Fig.4, and the MRCS of the conventional equal-height array is also given as reference. It can be observed from Fig.4 that the MFC method produces considerable RCS reduction at 11, 14.6, and 6 GHz which contributes to low scattering performance over a wide frequency band. The three frequency points with the minimum MRCS are 2—3 GHz higher than the design due to the mutual coupling under asymmetric arrangement. This problem can be solved by optimization in practical designs. It can be seen in Fig.5 that asd1decreases from 9.375 mm to 6.25 mm whiled2andd3remain unchanged, the cancellation frequencyf1increases from 11 GHz to 12.5 GHz accordingly. So, by optimizingdi, we can shiftfito the desired frequency.

Fig.4 MRCS of 1×4 array with equal-height arrangement and MFC arrangement

Fig.5 MRCS of 1×4 array with MFC for the case of different decrease from 9.375 mm to 6.25 mm in X-band

It is worth noting that, in most cases, the frequency of detecting wave is unknown, which requires the antenna array to obtain low scattering performance over the whole operating band. Therefore, the average root mean square (RMS) value of RCS reduction can better reflect the overall effect of the stealth design method.

Fig.6 Geometry of 1×4 Vivaldi antenna array with equal-height arrangement, ladder arrangement and MFC

Fig.7 MRCS of 1×4 Vivaldi antenna array

To further investigate the effect of MFC method on planar arrays, 4×4 Vivaldi antenna arrays of 5 different cases are discussed as follows. The distances between elements inX-direction and inY-direction are both 21 mm. Overhead view of the array is shown in Fig.8.Z-coordinates of elements in arrays of each case are given in Table 1, among which,didenotes a quarter wavelength of cancellation frequencyfi. As we can see from Fig.8 and Table 1, Case 0 represents the conventional planar arrays and acts as reference. Cases 1 and 2 comprise the cancellation structure at 10 GHz in two different ways. The MFC method is employed in Cases 3 and 4, where adjacent elements inX-direction comprise cancellation structure atf2and inY-direction atf3. In Case 3,f2andf3are assigned to 8 GHz and 12 GHz. In Case 4,f2andf3are assigned to 9 GHz and 11 GHz.

Fig.8 Overhead view of 4×4 arrays

AntennaCase 0Case 1Case 2Case 3/4#10d1d13d2+3d3#20d1d13d2+2d3#30d103d2+d3#40d103d2#50d1d12d2+3d3#60d1d12d2+2d3#70d102d2+d3#80d102d2#900d1d2+3d3#1000d1d2+2d3#11000d2+d3#12000d2#1300d13d3#1400d12d3#15000d3#160000Cancellationfrequency/GHzNone10108,12/9,11

The MRCS of above 5 cases are shown in Fig.9. The average RCS reductions in Cases 1—4 are given in Table 2. By comparison, Cases 3,4 perform more than 5 dB additional RCS reduction than Cases 1, 2. As the MFC method increases the cancellation frequency points, Cases 3 and 4 have MRCS below -25 dB through the whole operating band. It is noted that, more antenna elements usually involve more cancellation structures, so the MFC method can be even more effective for the stealth design of middle- or large-scale antenna arrays.

dB

The MRCS inXOZ-plane in Cases 0, 3 and 4 are also investigated to study their scattering performance under oblique incident waves. It can be seen from Fig.10 that, the back scattering of the antenna array in Cases 3,4 is significantly reduced within ±60°. Similar low profile characteristic can be observed through the whole X-band.

Fig.10 MRCS of 4×4 array in Cases 0, 3 and 4 for the incident wave ranging from -90° to +90° in XOZ-plane (f=10 GHz)

It is noteworthy that, as the total energy is not reduced by the MFC method, the reduction in RCS in a certain angle region will lead to the increase in RCS in other angle regions. We compare the bistatis radar cross section (BRCS) of Case 4 with that of Case 0. The co-polarized incident wave comes fromZ-direction at 10 GHz.

As shown in Fig.11, the main lobe of scattering in Case 4 is significantly reduced due to the cancellation while the back lobe arise. Fortunately, the strong scattering in back lobe is not in the threatening angle region, and it can be diminished by employing radar absorbing materials.

The simulated radiation pattern of Case 0 and Case 4 is given in Fig.12. The phase differences of radiation wave between elements in Case 4 have been compensated in source. Results show that, the main lobe of radiation pattern has 2 dB enhancement but the side lobe has approximately 10 dB deterioration in E-plane. In addition, the back lobe is greatly reduced. In order to maintain the radiation performance, we set 90° phase difference between adjacent elements to compensate the phase difference caused by asymmetric arrangement. However, the compensation also leads to cancellation of radiation waves in back lobe direction for their 180° phase difference. In general, the antenna array keeps a favorable radiation pattern when employed with the MFC method.

Fig.11 BRCS of 10 GHz in Cases 0, 4

Fig.12 Radiation pattern of 10 GHz in Cases 0,4

3 Conclusions

A stealth design method based on MFC for UWB end-fire antenna array is proposed. Vivaldi antenna arrays of different scales are discussed as examples to validate the effectiveness of the proposed method. Results show that the MFC method produces average 17.6 dB RCS reduction on 1×4 array and 22.6 dB RCS reduction on 4×4 array, and favorable radiation characteristics are maintained. By optimizing theZ-coordinate of each element properly, significant RCS reduction covering the whole operating band can be achieved. Therefore, the proposed method can be a good candidate for the stealth design of UWB end-fire antenna array.

Acknowledgement

This work was supported in part by Nanjing University of Aeronautics and Astronautics Research Funding (No.Kfjj20150414).